Features

Cable synchronous/programmable fixed frequency

Opti-LOOPTM compensation can minimize COUT

± 1%output voltage accuracy [123 123 ]

Dual N -channel MOSFET synchronization driver

Wide Vin range: 4V to 36V operations

Voltage range: 0.8V to 6V

Internal current fold

Output over -pressure prying rod protection

Lock short -circuit shutdown timer

Failure option

Extremely low voltage drop operation: 99%duty ratio

[

123] Forced continuous control sales

Available programming soft start

Remote output voltage detection

Good power output (only

LTC1735 f) [123 [123 ]逻辑控制微功率关机：IQ lt;25μALTC1435引脚兼容

小部件变化

提供16引线窄SSOP，因此包装和

20引线TSSOP封装(Limited to LTC1735F)

Application

notebook and palm computer, PDA mobile phone and wireless modem

DC power distribution system

Instructions

LTC #174; 1735 is the regulator controller that drives the external N -channel power supply to drive an external N -channel power supply. The burst ModetM operation provides high -efficiency current under low load. The reference voltage with an accuracy of 0.8V and the future generation microprocessor. Opti-Loop compensation allows transient response to optimize output capacitors and ESR values. The operating frequency (which can be synchronized to 500kHz) is the external capacitor settings, allowing the maximum flexibility to optimize efficiency. Forced continuous control of sales to reduce noise and radio frequency interference, and can help the second winding adjustment by disable the operation of the emergencies. The protection function includes internal folding current limits, output over -pressure pry rods, and optional short -circuit shutdown. Soft startup capacitors that can be used to sort the power supply. Users can detect the resistor through external current. The wide input power range allows working between 4V and 30V (maximum 36V).

absolute axis ratio (Note 1)

Input power supply voltage (VIN) 36V to –0.3V

The upper drive power supply voltage ( Blind voltage) 42V to 0.3V

The switch voltage (SW) 36V to –5V

EXTVCC voltage 7V to —0.3v

The voltage driver voltage (booster switch) 7V to –0.3V

sensing+, sensing voltage 1.1 (Intvcc) to -0.3V

FCB Voltage (INTVCC+0.3V) to -0.3V

i, vosense voltage 2.7V to — 0.3V

run/ss, pgood (only LTC1735F)

Voltage: 7V to 0.3V

Peak driver output current lt; 10μs (TG, BG) 3A number

intVCC output current 50 mAh

The working environment temperature range [ 123]

LTC1735C 0 ° C to 85 ° C

LTC1735i/LTC1735E (Note 8) –40 ° C to 85 ° C

Jacking temperature (Note 2) 125 degrees Celsius [123) ]

Storage temperature range -65 ° C to 150 ° C

Lead temperature (welding, 10 seconds) 300 degrees Celsius

electrical characteristics

indicates that it is applicable to the entire operation The specification

The temperature range, otherwise the specification is TA 25 ° C. Vin 15V, vRun/ss 5V, unless there is another instructions.

Electricity

indicates the specifications suitable for the entire operation

The temperature range, otherwise the specifications are TA 25 ° C. Vin 15V, vRun/ss 5V, unless there is another instructions.

Note 1: The absolute maximum rated value means that the value device that exceeds life may be damaged.

Note 2: TJ calculates according to the environmental temperature TA and power

Dispel PDs according to the following formulas:

LTC1735CS, LTC1735IS: TJ TA+(PD110 ° C/W)

LTC1735gn, LTC1735ign, LTC1735EGN: TJ TA+(PD130 ° C/W)

LTC1735CF, LTC1735if: TJ TA+(PD110 ° C/W)

electrical characteristics

Note 3: LTC1735 is tested in a feedback loop, which will put the vosense error off the balance point (VITH 1.2V).

Note 4: Since the grid charge is transmitted at the switch frequency. See application information.

Note 5: COSC by measuring COSCCharging to test the oscillator frequency current (iOSC) and application formula:

Note 6: minimum guide time condition corresponds to 40%of the inductance peak to peak lines ≥IMAX (see the minimum lead time application application Precautions for information parts).

Note 7: Rising and decreased at 10%and 90%measurement. The delay time is measured at 50%.

Note 8: LTC1735E guarantees the performance specification from 0 ° C to 85 ° C. The operating temperature range between -40 ° C and 85 ° C are controlled by design, representation, and associations to determine statistical processes. The LTC1735i specifications are guaranteed throughout -40 ° C to 85 ° C working temperature range.

典型性能特征

[123 ] COSC: The frequency of external capacitors from this pin to the grounding device works.

RUN/SS: The combination of soft start and operation control. The capacitor sets the slope time to the full output current at this pin ground. The time is about 1.25s/μF. Forcing this pin below 1.5V will cause the device to close down. (For static information, see the current comment on the application information part.) When turning off all features, including INTVCC, it is disabled. Latchoff over -current protection is also triggered by this pin, as described in the application information part.

ITH: Error Putting Maca compensation points. The current comparator threshold increases with the increase of the control voltage. The nominal voltage range of the pin is 0 to 2.4 volts.

FCB: Forced continuous/synchronous input. Ten the pins that are used for continuous and synchronous operation. The ground should be used to use a second winding or INTVCC to enable the low load operation of the emergencies. A disabled mode operation is prohibited with a signal above 1.5VP -P, but it is allowed to skip the cycle at a low load current and synchronize the internal oscillator with the external clock. When this device is turned off, it is not allowed to drive the FCB pin (run/SS pins low). Small signal ground. All small signal components such as COSC, CSS, feedback allocation and loop compensation resistance and capacitors should be connected to this native needle. This pin should be connected to PGND in turn.

Vosense: Receive the resistance division of the feedback voltage output terminal from the outside.

Sense -: The current comparator ( -) input.

Sense+: (+) input of current comparator. Built -in

The offset between Sense - and Sense+Pipefoot

Use RSENSE to set the current check threshold.

PGOOD (only LTC1735F): Opening logic output.When the Vosense pin is not in the ± 7.5%range of its setting value. EXTVCC: Input connected to the internal switch of INTVCC. This switch is turned off and provided VCC power EXTVCC at any time higher than 4.7V. See the EXTVCC connection application information part in the reference. Do not exceed 7V when you turn on and make sure EXTVCC≤Vin.

PGND: Drive power ground. Connected to the bottom N -channel MOSFET, Shawitki's anode diode and CIN ( -) terminal.

BG: The bottom large current door driver N channel MOSFET. The voltage swing at this pin comes from ground to InTVCC.

INTVCC: Internal 5.2V regulator and EXTVCC output switch. The driver and control circuit consists of this voltage. Use 1 μF ceramic to disconnect the connection with the power supply ground to directly 4.7 μF or other low ESR capacitors directly adjacent to the integrated circuit.

VIN: The main power supply. It must be closely separated from the power supply. Open the underwriting node to the inductors and the self -lifting device capacitor. The voltage swing on this pin comes from the Schottky diode (external) voltage to the ground to the ground to the vehicle recognition number (VIN).

Production: Power supply to the upper module. The guide program electric container returns to this pin. The voltage swing at this pin is dropped from a diode below INTVCC to VIN+INTVCC.

TG: Large current grid driver used for top N -channel MOSFET. This is the output of a floating driver with voltage switching. It is equal to the southwest of INTVCC that is superimposed on the opening node voltage.

Operation (reference function map)

Main control circuit

LTC1735 adopts constant frequency and current mode step by step. During the normal operation, when the top is set at the oscillator, MOSFET is turned on when the main current comparator I1 resets the RS lock in each cycle. Peak induction I1 reset the current of RS 闩 locks from the voltage on the control pin 3 (ITH), which is the wrong output amplifier EA. The pin #9251; 6 (Vosense), as described in the pin function, allow EA to receive the output feedback voltage VFB from the external resistor division. When the load current increases, ventricular fibrillation will cause ventricular fibrillation relative to the 0.8V reference voltage, thereby increased the i -i voltage until the average electrical sensor current and the new load current. When the top MOSFET is closed, the bottom MOSFET is connected until any electrical sensor current starts to reverse, such as the current comparator i2, or the next cycle starts. The top MOSFET drive is powered by floating startup with capacitor CB. This capacitor is usually charged from the MOSFET when INTVCC via the external diode. With the vehicle identification number (VIN) Reduce the converter will try to open the top MOSFET continuously. A drop -off counter detects this situation and forces the top MOSFET to close about 500NS to charge the self -raising capacitor every 10 cycles every 10 cycles.

Operation (reference function map)

Drive sales 2 to close the main control circuit (run/ss) low. Release RUN/SS allows the internal 1.2 μA current source to charging soft startup capacitor CSS. The CSS reaches 1.5V, and the main control circuit is enabled to be restrained of the values u200bu200bof about 30%of its maximum voltage. As CSS continues to charge, the iTH is gradually rented again, allowing normal operations. If you have 70%to 4.1V of its final value after CSS charging, you can follow the application information part. The internal oscillator can be synchronized with an external oscillator to the clock of the FCB pin, which can be locked to a certain frequency between 90%and 130%of the nominal interest rate set by CAPACI TOSC. Overvoltage comparator OV can prevent transient hyper -transfer ( gt; 7.5%) and other more serious possibilities that cause output overvoltage. In this case, the top MOSFET is closed, and the bottom MOSFET is closed until the overvoltage conditions are cleared. The output short -circuited reverse current limit is provided by the amplifier A. When Vosense drops below 0.6V, the i -i buffer input of the current comparator gradually drops to 0.86V clamping. This reduces the peak electrocompany current about 1/4 of its maximum value

Low -current operation

LTC1735 has three low -current modes, which are poured by FCB. When the FCB pin is higher than 0.8V (usually connected to INTVCC). Suddenly mode operation, if the error amplifier drives the voltage of the i -i voltage below 0.86V, the i -i buffer input of the current sealing device will be cut to 0.86V. The electrical sensor current is kept at about 20mV/RSense (about 1/4 of the maximum output current). If ITH drops to 0.5V, an emergency mode comparator B will turn off the MOSFET that maximizes the efficiency simultaneously. The load current is only from the output capacitor until the ITH increases higher than 60mV, and the stasis of the comparator and the switch recovers. The emergency mode operation is disabled when the FCB pin is lower than 0.8V, the comparator F. This forces continuously running and helps to adjust the second winding.

When the FCB pin is driven by the external oscillator, the low noise cycle skip mode is called, and the oscillator is synchronized with the external clock through a communication separator C. In this mode, the minimum inductance is 25%remove the current clamp, which provides a non -continuous operating current range on the broader output as much as possible. This constant frequency operation is not equivalent to the efficiency of emergencies operation, but it provides low noise and constant spectrum. The FCB sales can be forced on the ground. This is the lowest efficiency model, but it is also desirable in some applications. Output can be source orIt is the current in this mode. When continuously running at the current softening current under compulsory conditions, the current will be forced to return to the main power supply may increase the input power supply to the dangerous voltage level.

Reverse current, short -circuit detection and short -circuit atresia

Run/SS capacitor CSS was originally used to limit the flow of the switching regulator. When the controller starts and has enough time to charge the output capacitor and provide a full -load current, CSS is used as a short -circuit timeout circuit. If the output voltage drops to the voltage below 70%of its nominal output, the assumption of the CSS starts to discharge is that the output is in a current and/or short circuit state. If this situation lasts enough, it is determined by the size of the CSS, and the controller will be closed until the RUN/SS pin voltage is recycled. The compliance between the built -in LATCHOFF and the RUN/SS pin can be covered by providing a current with a current of more than 5μA. This current shorten the soft start time, but also prevents CSS from net discharge conditions during over current and/or short circuit. Whether the output voltage is lower than the 70%short -circuit lock circuit of its nominal level.

INTVCC/EXTVCC power supply

At the top and bottom MOSFET driver and MOST power supply LTC1735 internal circuit INTVCC pin. When the ExtVCC pin is kept open, the internal 5.2V low -voltage differential rejection device begins with the INTVCC power supply starting from VIN. If EXTVCC rises above 4.7V, the internal regulator is closed, and the internal switch is connected to EXTVCC to INTVCC. This makes the efficient energy, such as the first or second output of the converter to provide INTVCC power. The voltage is as high as 7V Can applied to EXTVCC to obtain additional grid driving capabilities. Provide clean startup and protect MOSFET. The underwriting lock is used to keep the two MOSFET off until the input voltage is higher than 3.5V. When the PGOOD (only LTC1735F) window comparator monitor the output voltage and its opening leakage output is pulled down, the divertal drop output voltage is not 0.8 volts in the range of ± 7.5%of the reference voltage.

ATIO application

The basic application circuit of LTC1735 is shown in the first page as shown in Figure 1. Drive the external parts to select Ruisen according to the load requirements. Once you know RSENSE, COSC and L can be selected. Next, choose power MOSFET and D1. The selection of this working frequency and sensor depends on the ripple current volume of the required ripples to a large extent. In the end, CIN is because it can handle large -balanced square root current replacement flowers and COUT choices that are low enough ESR to meet the output voltage ripples and transient specifications. The circuit shown in Figure 1 can operate the operation of up to 28V input voltage (due to external MOSFET).

The RSENSE select

Select RSENSE according to the required output current.The maximum threshold of the LTC1735 current comparator is 75MV/RSENSE, and the input co -mode range is SGND to 1.1 (INTVCC). The threshold of the current comparator sets the peak of the electrical sensor current, which generates the maximum value of the average output current IMAX equal to the peak minus half of the peak ripple current, #8710; IL. Allows LTC1735 and external component values:

The operating frequency and

The choice of operating frequency and inductance value is efficiency and components Between dimensions. Low -frequency operations reduce the MOSFET switch loss, including grid charge loss and transition loss. However, low -frequency operation requires more inductance currents under a given ripple amount.

LTC1735 uses a constant frequency architecture

The frequency determined by an external oscillator capacitor. Each time the upper MOSFET is turned on, the voltage on the COSC is reset to ground. At time, COSC is charged from fixed current. When the voltage reaches 1.19V, COSC reset ground. Then repeat this process. The value of COSC is based on the assumptions calculated by the expected operation. The frequency of the external clock input on the FCB:

Select the relationship of cosc u200bu200band the frequency. Figure 2 shown. The recommended maximum switching frequency is 550kHz.

The internal oscillator runs in its nominal frequency (FO)

When the FCB pin is pulled up to INTVCC or connected to the ground. The time to make the FCB pin above 0.8V and below will inject the internal oscillator into the clock signal of the external application to the FCB pin, and the frequency is between 0.9FO and 1.3FO. The clock high level must exceed 1.3V, at least 0.3 μs, and the low level of the clock must be less than 0.3V at least 0.3 μs. The opening of the top MOSFET will synchronize with the clock rising along. Try to synchronize to high external frequencies (higher than 1.3FO) will cause insufficient slope compensation and possible ring circuit unstable. If this situation exists only when the COSC value is low, the Fext FO is shown in Figure 2.

When synchronizing with the external clock, the emergency mode operation is disabled, but the sensor current does not allow reversal. The 25%minimum electricator current removes the fixture in the emergencies operation, which provides a constant frequency interrupted operation within the maximum output current range. Synchronize the MOSFET in this mode for each 10 clock cycle to charge the self -lifting capacitor. This is as high as possible to reduce noise efficiency at the same time as reasonable maintenance.

Calculation of inductor value

The operating frequency and the selection of sensors are interconnected, because higher operating frequency allows the use of inductance and capacitance to be less. So why is anyone choosing a larger part of working at a lower frequency? The answer is efficiency. Higher frequencyIt usually causes reduction in efficiency because MOSFET grid charge loss. In addition to this basic trade off, the impact of inductance value on ripple current must also consider the current operation. The inductance value has a direct impact on the ripple current. This inductive ripple current #8710; IL decreases with the increase of the inductance or frequency, and increases with the increase of VIN or VOUT:

Accept larger #8710; IL Value allows the use of low inductances, but can cause higher output voltage ripples and larger core losses. A reasonable starting point tidal wave current is #8710; IL 0.3 to 0.4 (IMAX). Remember, the maximum #8710; IL appears under the maximum input voltage. The inductance value also affects low -current. Began to turn to low -current running as an inductor current to zero and the bottom MOSFET. When the required average electrical sensor current generates a peak current than 25%of the current limit determined by RSENSE. The lower inductor value (higher #8710; IL) will cause this situation to occur under high load current, which will cause efficiency to decrease at the upper limit of low -current operation. When operating in an emergency mode, the lower inductance value will cause the explosion to decrease the frequency.

The electromat iron core selection

Once the value of L is known, the type of induction must be selected. High -cost iron hearts are generally not found in low -loss iron hearts, forcing the core of more expensive ferrite, molybdenum alloy or kool Mμ #174; core. Actual iron heart loss and iron heart size are a fixed inductor value, but it is very dependent on choosing an inductance. As the inductance increases, the loss of iron heart decreases. Unfortunately, the increased inductance requires more wire turns, so copper loss will increase.

Iron oxygen design has very low iron heart loss, which is the first choice at high switching frequency. Therefore, the design target can be concentrated in copper loss and prevent saturation. The ""inductance"" of ferrite refers to the ""iron core design when the current collapses suddenly"". This caused the inductors to suddenly increase the ripple current and the output voltage ripples that came. Do not let the core saturate! Molypermalloy (from Magnetics, Inc.) Is a very low but more expensive iron oxygen than the material. The reasonable compromise solution of the same manufacturer is KOOL MM. The ring is very space -saving, especially when you can use several layers of wires. Because they generally do not have a line axis, it is difficult to install. However, the design of the surface paste is not significantly increased. Power MOSFET and D1 must choose two external power MOSFETLTC1735: The top is n -channel MOSFET

(main) switch and the bottom N -channel MOSFET switch.

The peak grid pole driver level is set by INTVCC. During startup, the voltage is usually 5.2V (see EXTVCC pin connection). Therefore, in most LTC1735 applications, the logic level threshold must be used for old MOSFET. The only exception is when the low input voltage expects (VIN LT; 5V); then, the sub -logical level threshold should be used by MOSFET (VGS (Th) LT; 3V). Clear attention to the BVDSS specifications of MOSFETS AS specifications for many logic levels of MOSFET limited to 30V or less. The selection standard for power MOSFET includes the ""ON"" resistance RDS (ON), reverse transfer capacitor CRS, input voltage and maximum output current. When the LTC1735 runs the top and bottom MOSFET calculation formula under the continuous mode of the working cycle:

The power loss current under the maximum output of the MOSFET The temperature dependencies of RDS (on) and K are constants that are inversely proportional to the gate -drive current. Both MOSFETs have I2R loss N channel equations include an additional transmission loss, which is the highest at high input voltage. For VIN LT; 20V high -current efficiency generally improves for larger MOSFETs, and the transitional loss of VIN GT; 20V has increased rapidly to higher -point RDS (ON) devices with lower CRS (ON) devices actually provides higher CRS efficiency. Synchronous MOSFET loss is maximum at a high input voltage or short circuit, the duty cycle of this switch is close to 100%. Terms (1+Δ) are usually used in the form of standardized RDS (on) and temperature curves, but Δ #9251; 0.005/° C can be used as low -voltage MOSFET. CRS is usually in MOSFET features. The constant K 1.7 can be used to estimate the main switch loss equation. Figure 1 The Schartki diode D1 shows the dead area between the two power MOSFETs. This can prevent the body diode of the bottom MOSFET from opening and storing the charge efficiency of up to 1%during the dead area. 3A is the size of Shicky's usually 10A to 12A regulator because the relatively small average current. The larger diode will lead to an additional transitional loss caused by large knot capacitors. If the efficiency loss can tolerate

CIN selection

Under the continuous mode, the source current N -channel MOSFET at the top is a square wave with VOUT/VIN. In order to prevent large voltage transient, the size of the capacitor with a low ESR input maximum square root current must be used. The maximum equalized square root capacitor current is drawn from the following formula:

This formula has a maximum value when vin 2vout (Maximum)/2. This simple and worst case is usually used for design, because even major deviations will not provide too much relief. Please note that the volume of the wave current of the capacitor manufacturer is usually only based on 2000 hours of life. Therefore, it is recommended to further reduce the capacitor or choose the rated temperature higher than the compulsory. Several capacitors can also be parallel to meet the size or height requirements in the design.

COUT selection

The selection of COUT is mainly used by valid series resistance (ESR) to minimize voltage ripples. The output ripples in the continuous mode ( #8710; vout) are:

style, f operating frequency, COUT output capacitance, #8710; IL The ripple current in the inductor. Under the maximum input voltage of the output ripples, the maximum input voltage has been increased since #8710; IL. Generally, once ESR meets the requirements of COT, the average root current rating usually exceeds the requirements of Iriple (P -P). In the case of #8710; IL 0.3iout (maximum), 2/3 of the fluctuations for ESR, the output ripple under the maximum VIN will be less than 50mv assumption: the need for blood sinks lt; 2.2 RSENSECOUT GT; 1/(8FRSENSE)

The first condition is related to the ripple current that enters ESR. The second guaranteed output capacitor is not significant. Choosing to use smaller output capacitors will increase the ripple voltage caused by discharge, but it can maintain the ripple voltage by using ESR with a very low capacitor, which can be maintained or lower than 50 millivolttil. The aura compensation element of the i -i pin can be optimized to provide a stable and high -performance transient response without considering the selected output capacitance. The choice of CPU or other output capacitors with large load current transients is mainly loaded. The capacitor's resistor element, multiplied by load current, plus any output voltage ripple must be in the load (CPU).

The ESR required for the load current step is: Resr LT; #8710; V/ #8710; #8710; V is a allowable voltage deviation (excluding any drooping caused by limited capacitors). The maximum energy stored in the sensor is required. The capacitor must be enough to absorb the changes in the electrical sensor current when the transition from a large current to a small current occurs. This reverse load current conversion is usually controlled by the control loop OPTI-LOOP component, so make sure not to over-compensate and slow down the reaction. The minimum capacitor of this guarantee energy sensor is to fully absorb:

type #8710; i is a change in the load current.

Manufacturers such as Nichkang, United Chemistry Company, and Sanyo can consider using high -performance pass capacitors. The capacitors provided by OS-Con semiconductor electrolyte Sanyo have the lowest (ESR) (size) aluminum electrolyte higher price. Paided ceramic capacitors for OS-CON capacitors, it is recommended to reduce the inductance effect. In the surface installation application, ESR, RMS current transformersEntrepreneurship and looping specifications may require multiple parallel containers. Aluminum electrolytic, the surface of the dry 有 has a special polymer capacitor installation software package. Special polymer surface paste installed capacitors provide very low ESR, but have lower capacitor units of volume density than other types of capacitors. These capacitors provide a very economical and effective output capacitor as a controller with high -circuit bandwidth.高 The capacitor has the highest capacitor density and is usually used as an output capacitor for the switching regulator. Several excellent waves of wave test selection of AVX TPS, AVX TPSV, or Kemet T510 series surface installation of 钽钽 alloys, suitable for situations between 1.5 mm and 4.1 mm. Aluminum electrolytic capacitors can be used for cost -driven applications, provided by the rated value, temperature, and long -term reliability of pattern wave current. Typical applications will require several or more aluminum electrolytic containers. The combination of the above capabilities usually makes performance and reduction of overall costs. Other capacitors types include Nichkang PL series, NEC Neocap, Panasonic SP and Sprrag 595D series. Please consult the manufacturer for specific suggestions.

Like all components, the capacitor is not ideal. Each capacitor has its own advantages and limitations. The combination of different capacitor types proves economic efficient solutions. Remember to include high -frequency decoupling capacitors. They should be placed in the power of the power supply as close to the load as possible. The inductance in any circuit board trajectory is the use of negatives.

INTVCC regulator

The 5.2V power supply to power the drive and internal circuit power supply in the internal P channel low voltage species is within the LTC1735. INTVCC pins can provide a maximum square root current of 50mA, and must be bypass to at least 4.7 μF 钽, 10 μF specialty 钽 for grinding polymers or low ESR electrolytic capacitors. 1 μF ceramic capacitor is directly placed near INTVCC. It is strongly recommended to use PGND IC pins. In order to provide high transient current, good bypass needs to be used to need MOSFET gate drivers. The high -frequency driver of the high -input voltage of large MOSFETs may cause the maximum constitutional fixed value of the LTC1735 to exceed. System power supply current is often controlled by the gate charging current. The additional load also needs to consider the power dispersing calculation of INTVCC. The total INTVCC current can be input by 5.2V internal linear regulator or ExtVCC input pin. When the voltage is applied to the ExtVCC pin less than 4.7V, all INTVCC currents are powered by the internal 5.2V linear regulator. In this case, the consumption of integrated circuits is the highest: (VIN) (IintVCC) overall efficiency. The door fee depends on the operating frequency, such as the efficiency consideration. The knot temperature can be estimated by the equations given in use #9251; 2. For example, when the LTC1735CS is limited from 30V to less than 17mA, it is not used by EXTVCC pins, and power is used as follows: TJ 70 ° C+(17 mAh) (30 volts) (30 volts) (110 ° C/W) 126 ° C using the EXTVCC input pin to reduce the knot temperature to: TJ 70 ° C+(17 mAh) (5Volu